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The maximum gain at boresight for the lower band is 2/93 dBic at 2/5 GHz, while the gain for the upper band is 6/26 dBic at 3/52 GHz. The overall volume of the proposed antenna is 0/292λo × 0/292λo × 0/044λo, where λo is the corresponding free-space wavelength at 2/5 GHz.
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CP radiation is obtained from the patch antenna with its opposite corners chamfered. The perturbation introduced by the cut corners introduces an electric orthogonal field to the main field that is out of phase from it by 90°. This results in a rotating electric field and consequently CP radiation. The rotating electric fields can be visualized from Figures 8(a) and 8(b), which show the time-varying current distribution at the lower and upper frequencies, respectively. It can be seen that the lower frequency is radiated from the lower patch that is larger in size, while the higher frequency is radiated from the smaller upper patch.
The normalized radiation patterns for both the principal planes at the lower and upper frequency are shown in Figures 10 and 11, respectively. As the proposed antenna emits RHCP radiation, the RHCP pattern shows the copolarization level while the LHCP pattern indicates the cross-polarization level. At the lower frequency and at the boresight direction, the ratio of copolarization to cross-polarization level [RHCP − LHCP] over the AR bandwidth is better than 24 dB. At the upper frequency, the ratio of copolarization level is more than the cross-polarization level by 28 dB. The 3-dB CP beam width is more than 90°.
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In this paper, 50 ohm coaxial fed, stacked microstrip antenna over RIS is proposed and studied for CP radiation. The CP radiation in dual-bands (2/4 GHz ISM band and 3/5 GHz WiMAX band) with compact size is achieved using two truncated corner square patch radiators stacked over RIS. The RIS is used in the inductive region for decreasing the resonance frequency for the lower band and improving the antenna radiation performance. The compact CP patch antenna loaded with RIS is designed, fabricated, and tested. Commercially available electromagnetic (EM) solver CST Microwave Studio (MWS) , based on the finite integration technique (FIT), is used for designing and optimizing the proposed antenna design. This paper is divided into four sections following this introduction. Section 2 explains in detail the concept of artificial impedance surface (AIS), AMC, and RIS. Section 3 describes the design of the metasurface and the patch radiators and how both interact with each other. The simulated and measured results are discussed in Section 4. Section 5 concludes this paper by summarizing all the results obtained.
Keeping all the other parameters constant, the antenna was simulated with and without RIS. For an accurate comparison, the distance of the patch from the ground plane was kept the same in both the cases. The corresponding impedance bandwidth and gain plots are shown in Figures 7(a) and 7(b), respectively. It can be observed that the presence of the RIS directly affects the lower band, because the lower frequency is radiated from the lower patch that is kept directly over the RIS. The RIS causes the resonant frequency of the lower band to decrease, because of the coupling of the RIS’s inductive field with the patch radiator’s near-field capacitance. As the same length of patch now radiates at a lower operating frequency, it makes the electrical length of the patch smaller (because of the wavelength radiated being now larger). This also reduces the antenna’s gain slightly in the lower band, as that is a direct function of overall radiator size. The upper band is not affected by the RIS, as the patch radiator emitting that frequency is placed over a normal dielectric substrate. The use of RIS results in a 10% frequency reduction in the lower band. It also means that the radiation at the same frequency band can be obtained from a patch size smaller compared to the case without RIS.
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The lower patch has a length of mm and is chamfered by a length of mm. The coaxial feed is directly connected to the upper TCSP patch at a distance of and from the centre, while the lower TCSP patch is excited by EM coupling between the patches. All the antenna dimensions are summarized in Table 1. The CP radiation for the upper band (3/5 GHz WiMAX band) is emitted by the upper patch of smaller dimensions, while the radiation of the lower band (2/4 GHz ISM band) comes from the lower patch of larger dimensions. Just like the case with the metallic RIS arrays, a circular region is removed from the lower TCSP radiator. This prevents it from getting shorted to the feed.
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The upper and lower TCSP radiators are shown in Figure 6. The CP radiation is generated using square patches that have the upper-left and lower-right corners chamfered by a certain length. This generates two orthogonal modes that are out of phase by 90°, resulting in CP radiation.
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The measured 10-dB impedance bandwidth and 3-dB axial ratio graphs are shown in Figures 9(a) and 9(b), respectively. The impedance bandwidth for the lower band is from 2/39 to 2/59 GHz (8/1%), while the bandwidth in the upper band is from 3/38 to 3/62 GHz (6/9%). This is much more than the requirements of the ISM band and the WiMAX band, respectively. The AR bandwidth for polarization measured in the boresight (Φ = 0°, θ = 0°) is 2/40 to 2/55 GHz (6/1%) and 3/40 to 3/60 GHz (5/7%) for the lower and upper bands, respectively. Global bandwidth is defined as the range of frequencies that are common to the impedance bandwidth and the AR bandwidth. The AR bandwidth lies completely within the impedance bandwidth, so the global bandwidth is the same as the AR bandwidth. The RHCP gain at the boresight is 2/93 dBic at 2/50 GHz and 6/26 dBic at 3/52 GHz. The gain is almost constant over the global bandwidth, with a variation of 0/2 dB.
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The reflection phase graph of a metasurface shows the reflection phase for a particular frequency
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When the reflection phase is 180°, the metasurface behaves like a normal PEC
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Raw Gain falls off on lowest frequencies. High SWR on low and mid frequencies.
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